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Thinking of using it for either an induction heater or a dual resonant solid state tesla coil, but next up will be having to deal with annoying gate drive stuff first. submitted by /u/ieatgrass0 [link] [comments]

Київська політехніка зміцнює партнерство з Центральною школою Ліона kpi ср, 02/11/2026 - 18:25

There are many ways of generating analog sawtooth waveforms with oscillating circuits. Here’s a method that employs a single supply voltage rail to produce a buffered signal whose frequency can be varied over a range from 10Hz to 1MHz (Figure 1).

Figure 1 The sawtooth output waveform is the signal “saw” available at the output of op amp U1a. Its frequency is set by the value of resistor R6 which can vary from 120 Ω to 12 MΩ.

Wow the engineering world with your unique design: Design Ideas Submission Guide

U3, powered through R5, uses Q2 and R6 to create a constant current source. U3 enforces a constant voltage Vref of 1.2 V between its V+ and FB pins. Q2 is a high-beta NPN transistor that passes virtually all of R2’s current Vref/R6 through its collector to charge C3 with a constant current, producing the linear ramp portion of this ground-referenced sawtooth.

Op-amp U1 buffers this signal and applies it to an input of comparator U2a. The comparator’s other input’s voltage causes its output to transition low when the sawtooth rises to 1 volt. U2A, R1, Q1, R8, C1, and U2b produce a 100 ns one-shot signal at the output of U2b, which drives the gate of M1 high to rapidly discharge C3 to ground.

The frequency of the waveform is 1.2 / ( R6 ×  C3 ) Hz. With the availability of U3’s Vref tolerances as low as 0.2% and a 0.1% tolerance for R6, the circuit’s overall tolerances are generally limited by an at best 1% C3 combined with the parasitic capacitances of M1.

Waveforms at several different frequencies are seen in Figure 2, Figure 3, Figure 4, Figure 5, Figure 6, and Figure 7.

Figure 2 10 Hz sawtooth for an R6 of 12 MΩ.

Figure 3 100 Hz sawtooth for an R6 of 1.2 MΩ.

Figure 4 1 kHz sawtooth for an R6 of 120 kΩ.

Figure 5 10 kHz sawtooth for an R6 of 12 kΩ.

Figure 6 100 kHz sawtooth for an R6 of 1.2 kΩ.

Figure 7 1 MHz sawtooth for an R6 of 120 Ω.

Figures 3 and 4 show near-ideal sawtooth waveforms. But Figure 2, with its 12 MΩ R6, shows that even when “off,” M1 has a non-infinite drain-source resistance which contributes to the non-linearity of the ramp. It’s also worth noting that although U3’s FB pin typically pulls less than 100 nA, that’s the current that the 12 MΩ R6 is intended to source, so waveform frequency accuracy for this value of resistor is problematic.

Figures 5, 6, and 7 show progressive increases in the effects of the 100nS discharge time for C3 and of the finite recovery time of the op amp when its output saturates near the ground rail.

These circuits do not require any matched-value components. Accuracies are improved by the use of precision versions of R4, R6, R7, and U3, but the circuit’s operation does not necessitate these.

Christopher Paul has worked in various engineering positions in the communications industry for over 40 years.

Related Content

• Simple sawtooth generator operates at high frequency
• Adjustable triangle/sawtooth wave generator using 555 timer
• DAC (PWM) Controlled Triangle/Sawtooth Generator
• Another PWM controls a switching voltage regulator

The post Self-oscillating sawtooth generator spans 5 decades of frequencies appeared first on EDN.

A topic that has recently drawn a lot of interest (!) and no fewer than four separate design articles (!!) here in Design Ideas, is the conversion of 0 to 20mA current sources into industrial standard 4mA to 20mA current loop signals. Here’s the list—so far—in reverse chronological order. Apologies if (as is quite possible) I’ve missed one—or N.

• Another silly simple precision 0/20mA to 4/20mA converter
• Silly simple precision 0/20mA to 4/20mA converter
• Combine two TL431 regulators to make versatile current mirror
• A 0-20mA source current  to 4-20mA loop current converter

With so much energy already devoted to that one side of this well-tossed coin, it seemed only fair to pay a little attention to the flip side of the conversion function coin. Figure 1 shows the result. Its (fairly) simple circuit performs a precision conversion from 4-20mA to 0-20mA.  Here’s how it works.

Figure 1 The flip side of the current conversion coin: Iout = (IinR1 – 1.24v)/R2 = 1.25(Iin – 4mA).

Wow the engineering world with your unique design: Design Ideas Submission Guide

The core of the circuit is the Vin = IR1 = 1.24 V to 7.20 V developed by the 4-20mA input working into R1 and sensed by the Vref input of Z1. The principle in play is discussed in Figure 1 of “Precision programmable current sink.”

The resulting Z1 cathode current is (Iin R1 – Vref)/R2 = 0 to 20 mA as I increases from 4 mA to 20 mA. Or it would be if not for the phenomenon of Vref modulation by Z1 cathode voltage. The D1, Q2 cascode pair greatly attenuates this effect by holding Z1’s cathode voltage near zero and constant. It also extends Z1’s cathode voltage limit from an inadequate 7 V to the 30 V capability of Q2. Of course, a different choice for Q2 could extend it further.  But if 30 V will do, the >1000 typical beta of the 5089 is good for accuracy.

Current booster Q1 extends Z1’s 15 mA max current limit while also reducing thermal effects. The net result holds Z1’s maximum power dissipation to single-digit milliwatts.

With 0.1% precision R1 and R2 and the ±0.5% tolerance TLV431B, better than 1% accuracy can be achieved with the untrimmed Figure 1 circuit. If this level of precision is still inadequate, manual post-assembly trim can be added with just two extra parts, as shown in Figure 2. Calibration is achieved with one pass.

1. Set input current to 4.00 mA
2. Adjust R4 for output current of ~50 µA.  Note this is only 0.25% of full-scale, so don’t worry about hitting it exactly. You probably won’t.
3. Set input current to 20 mA
4. Adjust R5 for an output current of 20 mA

Figure 2 R4 and R5 trims allow post-assembly precision optimization.

Input max overhead voltage is 8 V, output overhead is 9 V. Worst case (resistor limited) fault current with 24 V supply = 80 mA.

Readers may notice a capacitor labeled “Ca” in Figures 1 and 2. This is the “Ashu capacitance” that Design Idea (DI) contributor and current source circuitry expert Ashutosh Sapre discovered to be essential for frequency stability of the cascode topology. Thanks, Ashu!

And a closing note. Since the output scale factor is set by and inversely proportional to R2, if any full-scale other than 20 mA is desired, it’s easily achieved by an appropriate choice for R2.

Stephen Woodward’s relationship with EDN’s DI column goes back quite a long way. Over 100 submissions have been accepted since his first contribution back in 1974.

 Related Content

• Another silly simple precision 0/20mA to 4/20mA converter
• Silly simple precision 0/20mA to 4/20mA converter
• Combine two TL431 regulators to make versatile current mirror
• A 0-20mA source current  to 4-20mA loop current converter

The post Full circle current loops: 4mA-20mA to 0mA-20mA appeared first on EDN.

HexaTech Inc of Morrisville, NC, USA (a subsidiary of Stanley Electric Co Ltd of Tokyo, Japan) has announced the immediate production release of its new 3-inch (76.2mm)-diameter single-crystal aluminium nitride (AlN) substrate product...

Many years ago, I overheard an engineer, with whom I had some project contact, make a casual remark about an RF connector situation, asking “what’s the big deal, it’s just a connector?” That statement was enough to make me wonder about his overall professional judgment.

Connectors may look simple but they are not, of course, as they must combine electrical requirements with mechanical issues and incorporate suitable materials for both body and contact. The materials and platings of their contacts are especially intricate as they blend metallurgical chemistry with other factors such as manufacturability, flexibility, resilience, and resistance objectives.

In recent years, there’s been an added demand on connectors: the need to be non-magnetic. Technically, this means the connector’s materials exhibit extremely low magnetic susceptibility, as they neither generate magnetic fields nor interact with external ones in any significant way.

Note that the term “magnetic connector” is also used for a connector/cable that relies on a magnetic force to both make and maintain a connection. In this arrangement, the plug and the socket have corresponding magnets or magnetic faces to make a self-aligning connection. They are designed for quick, easy, and, often, “break-away” disconnection to protect ports from wear and damage. But the magnetic/non-magnetic connectors here are not these.

Is it easy to visually distinguish a magnetic connector from a non-magnetic one? Maybe, maybe not. Some non-magnetic connectors have a different surface sheen or glow compared to conventional connectors, while others have different color (Figure 1). Of course, some magnetic ones also have a different color depending on the finish, so it’s not a certainty. Fortunately, magnetism is easy enough to test.

Figure 1 These two RF connectors are non-magnetic; other than their color, they look like magnetic connectors. So, color alone is not a definitive indicator. Source: Rosenberger Group

Even minute amounts of magnetic “interference” can have significant consequences in high-frequency or magnetically sensitive systems. Therefore, the objective of non-magnetic component design is to make these parts “magnetically invisible”. So, they don’t distort the surrounding field or interfere with nearby sensors or measurement instruments.

This is especially crucial in environments where magnetic fields play an active role, such as MRI systems, particle accelerators, and quantum computers:

• In MRI systems, magnetic components can distort the magnetic field lines, leading to degraded system performance, measurement inaccuracies, and artifacts in imaging results. In contrast, non-magnetic components minimize these disturbances by maintaining field uniformity.
• In precision RF and microwave metrology, magnetic components can bias sensor readings or create unpredictable phase errors. For example, a magnetic connector near a current probe could influence the magnetic coupling, altering the measured waveform.
• In systems such as scanning electron microscopes, where magnetic fields steer and direct the electrons to supercolliders, where superconducting magnets keep the particle centered as they are being accurate, the magnetic field must be precisely shaped and controlled.
• In the “hot” field of quantum computing, the qubits—the quantum bits that carry computational information—are extremely sensitive to external magnetic fields. Even minor magnetic impurities in nearby materials can cause decoherence, leading to computational errors or reduced qubit lifetime.

Non-magnetic connectors provide low–loss signal transmission and maintain stable performance across temperature cycles—without contributing to unwanted magnetic noise. In these cryogenic systems, even small amounts of magnetic interaction could invalidate experimental results.

A non-magnetic connector will typically have a low magnetic susceptibility of less than 10-5 (think back Electromagnetics 101: susceptibility is a dimensionless ratio) and a magnetic field strength of less than 0.1 milligauss. That’s at least one to two orders of magnitude less than standard connectors.

Making the non-magnetic connector

It may seem that all that’s required to make a non-magnetic connector is to use non-magnetic material such as copper. If only it were that easy, as non-magnetic materials have very different mechanical and electrical attributes, which affect connector performance and consistency.

A connector has three elements: the body, usually made of nylon or an engineered plastic and not a magnetic consideration; the contact or terminal pin, usually phosphor bronze, beryllium copper, or brass; and the surface plating(s), which can be copper, nickel, gold, tin, silver, palladium, or other metal.

The plating is the largest challenge, as it’s critical to long-term performance of the contact surfaces. The magnetic metals that are the concern here are iron, cobalt, and nickel, notes the Samtec video “Exploring Non-Magnetic Interconnects” (Figure 2).

Figure 2 Trouble zone in the periodic table: these three elements are the source of most of the magnetic problems. Solid-state physics analysis explains why this is so. Source: Samtec Inc.

The simple solution would be to avoid using these metals and instead use brass or aluminum for connector bodies with silver or gold plating. However, that’s often undesirable for performance reasons.

There are other options. For example, Samtec uses a nickel-phosphorus electrodeposited coating that works as a barrier layer between the copper-alloy base metal and subsequent outer layers. This barrier is needed to prevent migration of the copper to the surface-layer gold or tin of the connector pins, which would degrade the performance of that layer.

But wait—isn’t nickel one of the troublesome metals? Yes, but that’s where metallurgists bring some technical “magic” to the story. By adding phosphorus to the nickel, the ferromagnetism associated with high-purity nickel is reduced. This is because the added phosphorus interrupts the nickel’s atomic dipoles, causing the metal to become non-magnetic.

This is not the only option for going non-magnetic. Palladium provides a non-magnetic layer but is a costly alternative to nickel. Associated fasteners can be made of austenitic stainless steel (grades 304 or 316), which is non-magnetic due to its unique crystalline structure.

Other possibilities are eliminating the nickel completely, but this requires thicker copper and gold layers to slow the migration; use of a copper/tin/zinc alloy (Cu/Sn/Zn) called Tri-M3 as a barrier layer; or use of nickel-tungsten (Ni/W—tradename Xtalics). The goal is to reduce to grain size to nanoparticles and so disrupt the possibilities for alignment of the magnetic domains.

There are several ways to devise and fabricate non-magnetic connectors. It requires pure materials, deep-physics insight, metallurgical expertise, and precise control of production process. Assessing the non-magnetic characteristics involves sophisticated instrumentation to measure the magnetic permeability of the materials and connectors.

Each vendor has its own approach and a set of trade-offs regarding connector performance. Designers have many connector parameters to consider with respect to performance, solderability, number of mating cycles, supply-chain risk, and more.

The good news is that the increasing need for such connector means they are not items only available from one or two specialty suppliers. Nearly every manufacturer of RF connectors also offers non-magnetic versions, so users have many options for their connector needs and bill of materials.

What’s the price difference between magnetic and non-magnetic connectors? A quick, unscientific sampling showed that the non-magnetic ones were two to three times the price of their magnetic counterparts. It’s trivial to say that cost is a secondary concern in the applications where they are needed, but that is likely true.

Have you ever used non-magnetic connectors? Was the need for them identified in advance, or was it recognized after regular connectors were used, with problems identified and then linked to the magnetic connectors?

Certainly, the next time someone says, “it’s just a connector,” you can offer them firm evidence that’s not the case at all.

Related Content

• Consumer connectors get ruggedized
• Be aware of connector mating-cycle limits
• Giving Connector Contacts Adequate Consideration
• Through-hole connector resolves surface-mount dilemma
• Give Me Back My External Wi-Fi Antenna Connector, Please

The post Are non-magnetic connectors in your future? appeared first on EDN.

A major next step for artificial intelligence (AI) and machine learning (ML) innovation is moving ML models from the cloud to the edge for real-time inferencing and decision-making applications in today’s industrial, automotive, data center and consumer Internet of Things (IoT) networks. Microchip Technology has extended its edge AI offering with full-stack solutions that streamline the development of production-ready applications using its microcontrollers (MCUs) and microprocessors (MPUs) – the devices that are located closest to the many sensors at the edge that gather sensor data, control motors, trigger alarms and actuators, and more.

Microchip’s products are long-time embedded-design workhorses, and the new solutions turn its MCUs and MPUs into complete platforms for bringing secure, efficient and scalable intelligence to the edge. The company has rapidly built and expanded its growing, full-stack portfolio of silicon, software and tools that solve edge AI performance, power consumption and security challenges while simplifying implementation.

“AI at the edge is no longer experimental—it’s expected, because of its many advantages over cloud implementations,” said Mark Reiten, corporate vice president of Microchip’s Edge AI business unit. “We created our Edge AI business unit to combine our MCUs, MPUs and FPGAs with optimised ML models plus model acceleration and robust development tools. Now, the addition of the first in our planned family of application solutions accelerates the design of secure and efficient intelligent systems that are ready to deploy in demanding markets.”

Microchip’s new full-stack application solutions for its MCUs and MPUs encompass pre-trained and deployable models as well as application code that can be modified, enhanced and applied to different environments. This can be done either through Microchip’s embedded software and ML development tools or those from Microchip partners. The new solutions include:

• Detection and classification of dangerous electrical arc faults using AI-based signal analysis
• Condition monitoring and equipment health assessment for predictive maintenance
• Facial recognition with liveness detection supporting secure, on-device identity verification
• Keyword spotting for consumer, industrial and automotive command-and-control interfaces

Development Tools for AI at the Edge

Engineers can leverage familiar Microchip development platforms to rapidly prototype and deploy AI models, reducing complexity and accelerating design cycles. The company’s MPLAB X Integrated Development Environment (IDE) with its MPLAB Harmony software framework and MPLAB ML Development Suite plug-in provides a unified and scalable approach for supporting embedded AI model integration through optimised libraries. Developers can, for example, start with simple proof-of-concept tasks on 8-bit MCUs and move them to production-ready high-performance applications on Microchip’s 16- or 32-bit MCUs.

For its FPGAs, Microchip’s VectorBlox Accelerator SDK 2.0 AI/ML inference platform accelerates vision, Human-Machine Interface (HMI), sensor analytics and other computationally intensive workloads at the edge while also enabling training, simulation and model optimisation within a consistent workflow.

Other support includes training and enablement tools like the company’s motor control reference design featuring its dsPIC DSCs for data extraction in a real-time edge AI data pipeline, and others for load disaggregation in smart e-metering, object detection and counting, and motion surveillance. Microchip also helps solve edge AI challenges through complementary components that are required for product design and development. These include PCIe® devices that connect embedded compute at the edge and high-density power modules that enable edge AI in industrial automation and data centre applications.

The analyst firm IoT Analytics stated in its October 2025 market reportthat embedding edge AI capabilities directly into MCUs is among the top four industry trends, enabling AI-driven applications “…that reduce latency, enhance data privacy, and lower dependency on cloud infrastructure.” Microchip’s AI initiative reinforces this trend with its MCU and MPU platforms, as well as its FPGAs. Edge AI ecosystems increasingly require support for both software AI accelerators and integrated hardware acceleration on multiple devices across a range of memory configurations.

The post Microchip Extends its Edge AI Solutions for Development of Production-ready Applications using its MCUs & MPUs appeared first on ELE Times.

NUBURU Inc of Centennial, CO, USA — a developer of high-performance blue-laser technology and an emerging integrated defense & security platform provider — has completed the first tranche of a preferred equity restructuring transaction that materially simplifies its capital structure and reduces legacy balance-sheet overhang...

by Varun Bhatia, Vice President – Projects and Learning Solutions, Electronics Sector Skills Council of India. 

As India approaches its centenary in 2047, the idea of a Viksit Bharat has shifted decisively from aspiration to obligation. A 30 trillion-dollar economy, globally competitive manufacturing, integrated logistics, and digital universality are no longer distant goals. They are policy commitments.

Yet beneath every ambition lies a foundational truth. Development runs on dependable power. No country has crossed into developed-nation status on unreliable electricity. In India’s case, the transmission grid is not a supporting actor in this transformation. It is the stage itself.

The Grid That Holds the Nation Together

This transition from access to assurance has been enabled by a quiet but extraordinary expansion of India’s transmission network. India’s national power transmission system has crossed 5 lakh circuit kilometers, supported by 1,407 GVA of transformation capacity. Since 2014, the network has grown by 71.6 percent, with the addition of 2.09 lakh circuit kilometers of transmission lines and 876 GVA of transformation capacity. Integration at this scale has reshaped the energy landscape. The inter-regional power transfer capacity now stands at 1,20,340 megawatts, enabling electricity to move seamlessly across regions. This has successfully realized the vision of One Nation, One Grid, One Frequency and created one of the largest synchronized grids in the world. This architecture is not merely technical. It is economic infrastructure. It allows energy to flow from resource-rich states to industrial corridors without friction, strengthening productivity, investment confidence, and national competitiveness.

From Electrification to Excellence

India’s first power-sector revolution was about access, and that mission is largely complete. Saubhagya connected 2.86 crore households, while DDUGJY achieved universal village electrification by 2018. These were historic milestones.

However, access is only the starting point. Developed economies operate on a higher standard where power is always available, always stable, and always scalable. In a Viksit Bharat, outages must be exceptions rather than expectations. Voltage fluctuations cannot be built into business models. An industrial unit in rural Assam must receive the same quality of supply as one operating in an export hub in Southeast Asia. Reliability has now become the true benchmark of progress.

Rural India: From Load Centre to Growth Partner

The impact of a strong transmission backbone is most visible in rural India. Average rural power supply has increased from 12.5 hours per day in 2014 to 22.6 hours in FY 2025. This improvement has fundamentally altered the economic potential of villages and small towns. Reliability is being reinforced by systemic reforms. Under the Revamped Distribution Sector Scheme, grid modernization has reduced national AT&C losses to 15.37 percent, improving the financial sustainability of electricity supply.

Digital tools are accelerating this shift. More than 4.76 crore smart meters have been installed nationwide, bringing transparency, efficiency, and real-time control to energy consumption. Targeted interventions continue to close the remaining gaps. The PM-JANMAN initiative is electrifying remote habitations of Particularly Vulnerable Tribal Groups, while PM-KUSUM is reshaping agricultural power by enabling reliable daytime electricity through solarization. With states tendering over 20 gigawatts of feeder-level solar capacity, farmers are increasingly becoming urjadatas, contributing power back to the grid.

Reliable transmission makes this participation possible. The tower standing in a farmer’s field is no longer just infrastructure. It is a direct connection to the national economy. With assured round-the-clock power, industries no longer need to cluster around congested urban centers. Cold chains, food processing units, automated MSMEs, and digital services can operate efficiently in Tier-2 and Tier-3 towns. This urban transformation creates local employment, strengthens regional economies, and reduces migration pressures. In this model, rural India is no longer a subsidized consumer of power. It becomes a productive contributor to national growth.

Green Ambitions Need Grid Muscle

A Viksit Bharat must also be a sustainable Bharat. India’s commitment to achieving 500 gigawatts of non-fossil fuel capacity by 2030 reflects both climate responsibility and strategic foresight. Renewable energy, however, is geographically dispersed. Solar potential lies in deserts, wind along coastlines, and hydro resources in mountainous regions. Without a strong transmission backbone, clean energy remains stranded. The expanded grid, supported by investments under the Green Energy Corridor program, has become the central enabler of renewable integration. Strengthened inter-regional links ensure that clean power generated in remote areas can reach demand centers efficiently. This capability allows India to pursue growth without compromising its environmental commitments.

Resilience as National Security

Recent global energy shocks and climate-induced disruptions have reinforced one reality. Energy security is inseparable from national security. The grid of a developed India must therefore be resilient, intelligent, and adaptive. Smart Grids capable of self-healing, predictive maintenance, and advanced demand-response management are no longer optional. They are essential. Equally important is social resilience. Right-of-Way challenges require a partnership-driven approach. Landowners must be treated as stakeholders in national progress, with fair compensation and transparent processes that build trust and cooperation.

The Backbone of a Developed India

As India moves steadily toward 2047, development will be measured not only by economic output or industrial capacity, but by the consistency and quality of its power supply. Every kilometer of transmission line laid becomes a conduit for productivity. Every additional GVA of capacity strengthens energy security. The quiet hum of high-voltage lines signals a nation growing with confidence. Connecting Bharat is no longer about lighting homes. It is about powering aspirations, enabling enterprise, and securing India’s place as a self-reliant global force.

The transmission grid is not merely supporting the vision of Viksit Bharat. It is sustaining it.

The post The Grid as Strategy: Powering India’s 2047 Transformation appeared first on ELE Times.

Efficient Power Conversion Corp (EPC) of El Segundo, CA, USA — which makes enhancement-mode gallium nitride on silicon (eGaN) power field-effect transistors (FETs) and integrated circuits for power management applications — has announced a comprehensive licensing agreement with Renesas Electronics Corp of Tokyo, Japan, a global supplier of semiconductor solutions and high-voltage GaN transistors...

ELE Times conducts an exclusive interview with Rohit Bhan, Senior Staff Electrical Engineer at Renesas Electronics America, discussing how advanced sensing, 120 V power conversion, ±5 mV precision ADCs, and ASIL D fault-handling capabilities are driving safer, more efficient, and scalable battery systems across industrial, mobility, and energy-storage applications.

Rohit Bhan has spent two decades advancing mixed-signal and system-level semiconductor design, with a specialization in AMS/DMS verification and battery-management architectures. Over the past year, he has expanded this foundation through significant contributions to high-voltage BMIC development, helping to push Renesas’ next generation of power-management solutions into new levels of accuracy, safety, and integration.

Rohit is highly regarded within Renesas and industry-wide for his ability to bridge detailed analog modeling, digital verification, and real-world application requirements. His recent work includes developing ±5 mV high-accuracy ADCs for precise cell monitoring, implementing an on-chip buck converter that reduces board complexity, and architecting 18-bit current-sensing solutions that enable more advanced state-of-charge and state-of-health analytics. He has also integrated microcontroller-driven safety logic into verification environments—supporting ASIL D-level fault detection and autonomous response—while contributing to Renesas’ first BMIC design.

Rohit’s expertise spans behavioral modeling, reusable verification environments, multi-cell chip operation, and stackable architectures for even higher cell counts. His end-to-end perspective—ranging from system definition and testbench development to customer engagement and product innovation—has made him a key contributor to Renesas’ battery-management roadmap. As the industry moves toward higher voltages, smarter analytics, and tighter functional-safety requirements, his work is helping shape the next wave of intelligent, reliable, and scalable BMIC platforms.

Here are the excerpts from the interaction:

ELE Times: Rohit, you recently helped deliver a multi-cell BMIC architecture capable of operating at high voltage. What were the most significant engineering hurdles in moving to a new process technology for the first time, and what does that enable for future high-voltage applications?

ROHIT BHAN: From a design perspective, key challenges included managing high-stress device margins (such as parasitic bipolar effects and field-plate optimization), defining robust protection strategies for elevated operating conditions, integrating higher-energy power domains, maintaining analog accuracy across very large common-mode ranges, and working through evolving process design kit maturity. From a verification standpoint, this required extensive coverage of extreme transient conditions (including electrical overstress, surge, and load-dump-like events), which drove expanded corner matrices, mixed-signal simulation complexity, and tight correlation between silicon measurements and models to close the accuracy loop and ensure specified performance.

Looking forward, these advances enable future high-energy applications with increased monitoring and protection headroom, simpler system-level implementations, and improved measurement integrity. A mature high-stress-capable process combined with robust analog and IP libraries provides a scalable foundation for derivative products (such as variants with different channel densities or feature sets) and for modular or isolated architectures that support higher aggregate operating ranges—while preserving a common verification, validation, and qualification framework.

ELE Times: Among your 2025 accomplishments, your team achieved ±5 mV accuracy in cell-voltage measurement. Why is this level of precision so critical for cell balancing, battery longevity, and safety—especially in EV, industrial, and energy-storage use cases?

RB: If our measurement error is ±20 mV, the BMIC can “think” a cell is high when it isn’t or miss a genuinely high cell; the result is oscillatory balancing and residual imbalance that never collapses. Tightening to ±5 mV allows thresholds and hysteresis to be set small enough that balancing actions converge to a narrow spread instead of dithering. Over hundreds of cycles, that cell becomes the pack limiter (early full/empty flags, rising impedance). Keeping the max cell delta small via ±5 mV metrology lowers the risk of one cell aging faster and dragging usable capacity and power down. In addition, early detection of abnormal dV/dt under load or rest hinges on accurate voltage plateaus and inflection points—errors here mask the onset of dangerous behavior.

ELE Times: An on-chip buck converter is a major milestone in integration. How did you approach embedding such a high-voltage converter into the BMIC, and what advantages does this bring to OEMs in terms of board simplification, thermal performance, and cost?

RB: There are multiple steps involved in making this decision. It starts with finding the right process and devices, partitioning the power tree into clean voltage domains, and engineering isolation, spacing, and ESD for HV switching nodes. Finally, close the control loop details (gate drive, peak‑current trims, offsets) and verify at the system level, and correlate early in the execution phase.

For OEMs, this translates into simpler boards with fewer external components, easier routing, and a smaller overall footprint, while eliminating the need for external high-stress pre-regulators feeding the battery monitor, since the pack-level domain is managed on die. By internalizing the high-energy conversion and using cleaner harnessing and creepage strategies, elevated-potential nodes are no longer distributed across the board, significantly simplifying creepage and clearance planning at the power-management boundary. The result is fewer late-stage compliance surprises and integrated high-energy domains that are aligned with process-level reliability reviews, reducing the risk of re-layout driven by spacing or derating constraints. 

ELE Times: You also worked on an 18-bit ADC for current sensing. How does this resolution improve state-of-charge and state-of-health algorithms, and what new analytics or predictive-maintenance features become possible as a result?

RB: Regarding the native 18‑bit resolution and long integration window: the coulomb‑counter (CC) ADC integrates for ~250 ms (milliseconds) per cycle, with selectable input ranges ±50/±100/±200 mV across the sense shunt; results land in CCR[L/M/H] and raise a completion IRQ. This is the basis for low‑noise charge throughput measurement and synchronized analytics. Error and linearity you can budget: the EC table shows 18‑bit CC resolution, INL ~27 LSB, and range‑dependent µV‑level error (e.g., ±25 µV in the ±50 mV range), plus a programmable dead‑zone threshold for direction detection—so the math can be made deterministic. Cross‑domain sync: A firmware/RTL option lets the CC “integration complete” event trigger the voltage ADC sequencer, tightly aligning V and I snapshots for impedance/OCV‑coupled analytics.

Two main functionalities that depend on this accuracy are State of Charge (SOC) and State of Health (SOH). First, for SOC accuracy—following is where the extra bits show up:

1. Lower quantization and drift in coulomb counting: with 18‑bit integration over 250 ms, the charge quantization step is orders smaller than typical load perturbations. Combined with the ±25–100 µV error bands (range‑dependent), which reduces cycle‑to‑cycle SOC drift and tightens coulombic efficiency computation—especially at low currents (standby, tail‑charge), where coarse ADCs mis‑estimate.
2. Cleaner “merge” of model‑based and measurement‑based SOC: the synchronized CC‑→‑voltage trigger lets you fuse dQ/dV features with the integrated current over the same window, improving EKF/UKF observability when OCV slopes flatten near the top of charge. Practically: fewer recalibration waypoints and tighter SOC confidence bounds across temperature.
3. Robust direction detection at very small currents: the dead‑zone and direction bits (e.g., cc_dir) are asserted based on CC codes exceeding a programmable threshold; you can reliably switch charge/discharge logic around near‑zero crossings without chattering. That matters for taper‑charge and micro‑leak checks.

For SOH + predictive maintenance, this resolution enables capacity‑fade trending with confidence, specifically:

• Cycle‑level coulombic efficiency becomes statistically meaningful, not noise‑dominated—letting you detect early deviations from the fleet baseline.

• Impedance‑based health scoring (per cell and stack): enabling impedance mode in CC (aligned with voltage sampling) gives snapshots each conversion period; tracking ΔR growth vs. temperature and SOC identifies aging cells and connector/cable degradation proactively.

• Micro‑leakage & parasitic load detection: with µV‑level CC error windows and long integration, you can flag slow, persistent current draw (sleep paths, corrosion) that would be invisible to 12–14‑bit chains—preventing “vanishing capacity” events in ESS and industrial packs.

• Adaptive balancing + charge policy: fusing accurate dQ with cell ΔV allows balancing decisions based on energy imbalance, not just voltage spread. That reduces balancing energy, speeds convergence, and lowers thermal stress on weak cells.
• Early anomaly signatures: the combination of high‑resolution CC and triggered voltage sequences yields load‑signature libraries (step response, ripple statistics) that expose incipient IR jumps or contact resistance growth—feeding an anomaly detector before safety limits trip.

ELE Times: Even with high-accuracy ADCs, on-chip buck converters, and advanced fault-response logic, the chip is designed to minimize quiescent current without compromising monitoring capability. What design strategies or architectural decisions enabled such low power consumption?

RB: We achieved very low standby power through four key strategies. First, we defined true power states that completely shut down high-consumption circuitry, such as switching regulators, charge pumps, high-speed clocks, and data converters. Second, wake-up behavior is fully event-driven rather than periodically active. Third, the always-on control logic is designed for ultra-low leakage operation. Finally, voltage references and regulators are aggressively gated, so precision analog blocks are only enabled when they are actively needed. Deeper low-power modes further reduce consumption by selectively disabling additional domains, enabling progressively lower leakage states for long-term storage or shipping scenarios.

ELE Times: You’ve emphasized the role of embedded microcontrollers in both chip functionality and verification. Can you explain how MCU-driven fault handling—covering short circuits, overcurrent, open-wire detection, and more—elevates functional safety toward ASIL D compliance?

RB: In our current chip, safety is layered so hazards are stopped in hardware while an embedded MCU and state machines deliver the diagnostics and control that raise integrity toward ASIL D. Fast analog protection shuts high‑side FETs on short‑circuit/overcurrent and keeps low‑frequency comparators active even in low‑power modes, while event‑driven wake and staged regulator control ensure deterministic, traceable transitions to safe states.

The MCU/FSM layer logs faults, latches status, applies masks, and cross‑checks control vs. feedback, with counters providing bounded detection latency and reliable classification—including near‑zero current direction via a programmable dead‑zone. Communication paths use optional CRC to guard commands/telemetry, and a dedicated runaway mechanism forces NORMAL→SHIP if software misbehaves, guaranteeing a known safe state. Together, these mechanisms deliver immediate hazard removal, high diagnostic coverage of single‑point/latent faults, auditable evidence, and controlled recovery—providing the system‑level building blocks needed to argue ISO 26262 compliance up to ASIL D.

ELE Times: Stackable BMICs are becoming a major focus for high-cell-count systems. What challenges arise when daisy-chaining devices for applications like e-bikes, industrial storage, or large EV packs, and how is your team addressing communication, synchronization, and safety requirements?

RB: Stacking BMICs for high‑cell‑count packs introduces tough problems—EMI and large common‑mode swings on long harnesses, chain length/topology limits, tighter protocol timing at higher baud rates, coherent cross‑device sampling, and ASIL D‑level diagnostics plus safe‑state behavior under hot‑plug and sleep/wake. We address these with hardened links (transformer for tens of meters, capacitive for short hops), controlled slew and comparator front‑ends, ring/loop redundancy, and ASIL D‑capable comm bridges that add autonomous wake; end‑to‑end integrity uses 16/32‑bit CRC, timeouts, overflow guards, and memory CRC. For synchronization, we enforce true simultaneous sampling, global triggers, and evaluate PTP‑style timing, using translator ICs to coordinate mixed chains.

ELE Times: You have deep experience building behavioral models using wreal and Verilog-AMS. How does robust modeling influence system definition, mixed-mode verification, and ultimately silicon success for high-voltage BMICs?

RB:  Robust wreal/Verilog‑AMS modeling is a force multiplier across the mixed signal devices. It clarifies system definition (pin‑accurate behavioral blocks with explicit supplies, bias ranges, and built‑in checks), accelerates mixed‑mode verification (SV/UVM testbenches that reuse the same stimuli in DMS and AMS, with proxy/bridge handshakes for analog ramp/settling), and de‑risks silicon by catching integration and safety issues early (SOA/EMC assumptions, open‑wire/CRC paths, power‑state transitions) while keeping sims fast enough for coverage.

Concretely, pin‑accurate DMS/RNM models and standardized generators enforce the right interfaces and bias/inputs status (“supplyOK”, “biasOK”), reducing schematic/model drift. SV testbenches drive identical sequences into RNM and AMS configs for one‑bench reuse so timing‑critical behaviors are verified deterministically. RNM delivers order‑of‑magnitude speed‑ups (e.g., ~60× seen in internal comparisons) to reach coverage across modes. Model‑vs‑schematic flows quantify correlation (minutes vs. hours) and expose regressions when analog blocks change. Together with these practices in our methodology and testbench translates into earlier bug discovery, tighter spec alignment, and first‑time‑right outcomes.

ELE Times: Your work spans diverse categories—from power tools and drones to renewable-energy systems and electric mobility. How do application-specific requirements shape decisions around cell balancing, current sensing, and protection features?

RB: Across segments, application realities drive our choices: power tools and drones favor compact BOMs and fast transients, so 50 mA internal balancing with brief dwell and measurement settling, tight short‑circuit latency, and coulomb‑counter averaging for SoC works well; e‑bikes/LEV typically stay at 50 mA but require separate charge vs. discharge thresholds (regen vs. propulsion), longer DOC windows and microsecond‑class SCD cutoffs to satisfy controller safety timing. Industrial/renewables often need scheduled balancing and external FET paths beyond 50 mA, plus deep diagnostics (averaging, CRC, open‑wire) across daisy‑chained stacks and EV/high‑voltage packs push toward ASIL D architectures with pack monitors, redundant current channels, contactor drivers, and ring communications. Current sensing is chosen to match the environment—low‑side for cost‑sensitive packs, HV differential with isolation checks in EV/ESS—while an 18‑bit ΔΣ coulomb counter and near‑zero dead‑zone logic preserve direction fidelity. Protection consistently blends fast analog comparators for immediate energy removal with MCU‑logged recovery and robust comms (CRC, watchdogs), so each market gets the right balance of performance, safety, and serviceability.

ELE Times: As battery management and gauges (BMG) evolve toward higher voltages, embedded intelligence, and greater integration, what do you see as the next major leap in BMIC design? Where are the biggest opportunities for innovation over the next five years?

RB: This is an exciting topic. Based on our roadmaps and the work we have been doing, the next major leap in BMIC design is a shift from “cell‑monitor ICs” to a smart, safety‑qualified pack platform—a Battery Junction Box–centric architecture with edge intelligence, open high‑speed wired communications, and deep diagnostics that run in drive and park. Here’s where I believe the biggest opportunities lie over the next five years:

• Pack‑centric integration: the Smart Battery Junction Box
• Communications: from proprietary chains to open, ring‑capable PHY
• Metrology: precision sensing + edge analytics
• Functional safety that persists in sleep/park
• Power: HV buck integration becomes table stakes
• Balancing: thermal‑aware schedulers and scalable currents
• Cybersecurity & configuration integrity for packs
• Verification‑driven design: models that shorten the loop.

The post Engineering the Future of High-Voltage Battery Management: Rohit Bhan on BMIC Innovation appeared first on ELE Times.

Anritsu Corporation released a new RF hardware option for its Radio Communication Test Station MT8000A to support the key FR3 (Frequency Range 3) frequency band for next‑gen 6G mobile systems. With this release, the MT8000A platform now supports evolving communications technologies, covering R&D through to final commercial deployment of 4G/5G and future 6G/FR3 devices.

Anritsu will showcase the new solution in its booth at MWC Barcelona 2026 (Mobile World Congress), the world’s largest mobile communications exhibition, held in Barcelona, Spain, from March 2 to 5, 2026.

Since 6G is expected to deliver ultra-high speed, ultra-low latency, ultra-safety and reliability far surpassing 5G, worldwide, international standardisation efforts are accelerating toward commercial 6G release.

The key high‑capacity data transmission and wide-coverage features of 6G require using the FR3 frequency band (7.125 to 24.25 GHz), and the Lower FR3 band range up to 16 GHz, which extends from the FR1 (7.125 GHz) band, is already on the agenda for the 2027 World Radiocommunication Conference (WRC-27) discussions.

By leveraging its long expertise in wireless measurement, Anritsu’s MT8000A test platform leads the industry with this highly scalable new RF hardware option supporting the Lower FR3 band, and covering both current and next‑generation technologies. Future 6G functions will be supported by seamless software upgrades, helping speed development and release of new 6G devices.

Development Background

The FR3 frequency band is increasingly important in achieving practical 6G devices, meaning current 4G/5G test instruments (supporting FR1 and FR2) require hardware upgrades.

Additionally, dedicated FR3 RF tests are required because FR3 and conventional FR1/FR2 bands have different RF-related connectivity and communication quality features.

Furthermore, FR3 test instruments will be essential for both 6G protocol tests to validate network connectivity, and for functional tests to comprehensively evaluate service/application performance.

These factors are driving demand for a highly expandable, multifunctional, and high‑performance test platform like the MT8000A, covering both existing 4G/5G devices and next‑generation multimode 4G/5G/6G devices.

Product Overview and Features

Radio Communication Test Station MT8000A

The current MT8000A test platform supports a wide range of 3GPP-based applications, including RF, protocol, and functional tests for developing 4G/5G devices.

By adding this new industry-beating RF hardware option supporting 6G/Lower FR3 bands, Anritsu’s MT8000A platform assures long‑term, cost-effective use for developing future 6G/FR3 devices.

Anritsu’s continuing support for future 6G/FR3 test functions using MT8000A software upgrades will advance the evolution of next‑generation communications and help achieve a useful, safe, and stable network‑connected society.

The post Anritsu Launches New RF Hardware Option, Supporting 6G FR3  appeared first on ELE Times.

Марія Зуєва: "КПІ сприяє формуванню професійної компетентності та характеру" Інформація КП ср, 02/11/2026 - 09:00

it's displaying GHIJKL on the display. The display is a Maxwell MAX7219 7 segment display run from an ESP8266 generic. I had to write my own driver so I could show what I wanted via the letter and not binary literal. Am I a look submitted by /u/DiodeInc [link] [comments]

Violumas Inc of Fremont, CA, USA, a provider of high-power UV LED solutions and inventor of 3-PAD LED technology, has released its next-generation 255nm, 265nm and 275nm LEDs in both SMD and COB configurations...

Violumas Inc of Fremont, CA, USA, a provider of high-power UV LED solutions and inventor of 3-PAD LED technology, has released its next-generation 255nm, 265nm and 275nm LEDs in both SMD and COB configurations...

It is well known that a 555 timer in astable mode can be frequency modulated by applying a control voltage (CV) to pin 5. The schematic on the left of Figure 1 shows this classic 555 VCO. 

Figure 1 Classic VCO (left) and new 555 VCO variant (right), where Pin 5 is not modulated, which leads to a constant 50% pulse width, independent of frequency.

Modulating pin 5 has some severe drawbacks: The control voltage (CV) must be significantly > 0 V and < V+, otherwise the oscillation stops.

Wow the engineering world with your unique design: Design Ideas Submission Guide

In contrast to a typical VCO, which outputs 0 Hz or Fmin @ CV=0 and reaches Fmax @ CVmax, the CV behavior of the classic 555 VCO is inverted and nonlinear. This is due to the modulation of the upper and lower Schmitt trigger thresholds, and pulse width changes with frequency. The useful tuning range Fmax/Fmin is limited to about 3.

Stephen Woodward’s “Can a free-running LMC555 VCO discharge its timing cap to zero?” shows some clever improvements: linear-in-pitch CV behavior and an extended 3 octave range, but still suffers from other “pin 5” drawbacks.

The schematic on the right of Figure 1 shows a new variant of the 555 VCO. Pin 5 is not modulated, which leads to a constant 50% pulse width, independent of frequency.

A rising CV results in a higher frequency. CV=0 is allowed and generates Fmin.

The useful tuning range is >10 and ≥100, with some caveats noted below.

Although it uses only 2 resistors and 1 capacitor, like the classic 555 astable configuration, it is a bit harder to understand. The basic function of adding a fraction of the square wave output voltage to the triangle voltage over C, which rises in frequency, is described in my recent Design Idea (DI), “Wide-range tunable RC Schmitt trigger oscillator.”

There, I use a potentiometer to add a fraction of the output to the capacitor voltage.

In the new 555 VCO variant, the potentiometer voltage is replaced by an external CV, which is chopped by the 555 discharge output (pin 7).

When CV is 0, the voltage on the right side of C3 is also 0, and the VCO outputs Fmin. With rising CV, a square wave voltage between 0V (pin 7 discharging) and CV (pin 7 open) appears on the right side of C3. Similar to my above-mentioned DI, this square wave voltage must always be smaller than the hysteresis voltage  (555: Vh=V+/3), otherwise Fmax goes towards infinity. That is why you must watch your CVmax if you want to reach high Fmax/Fmin ratios.

Figure 2 shows a QSPICE simulation of frequency with respect to CV from 0 V to 3.9 V in 100 mV steps.

Figure 2 QSPICE simulation of frequency with respect to CV from 0 V to 3.9 V in 100 mV steps.

A prototype with component values from Figure 1  and V+=12 V has been breadboarded, and a rough frequency-versus-CV curve is measured and marked with a red dot in the QSPICE simulation in Figure 2.

Figure 3 shows a scope screenshot for Fmin. 

Figure 3 A scope screenshot for Fmin, CH1 (yellow) output voltage, CH2 (magenta) CV=0.

In conclusion, the new 555 VCO circuit overcomes some drawbacks of the classic version, like limited CV range, inverted CV/Hz behavior, and changing pulse width, without using more components. Unfortunately, it still shows nonlinear CV/Hz behavior. Maybe using a closed loop, with an opamp and a simple charge pump, can tame it by raising the chip count to 2.

Uwe Schüler is a retired electronics engineer. When he’s not busy with his grandchildren, he enjoys experimenting with DIY music electronics.

Related Content

• Can a free-running LMC555 VCO discharge its timing cap to zero?
• Wide-range tunable RC Schmitt trigger oscillator
• A pitch-linear VCO, part 1: Getting it going
• A pitch-linear VCO, part 2: taking it further
• A two-way mirror—current mirror that is

The post 555 VCO revisited appeared first on EDN.

Infineon Technologies AG of Munich, Germany has published the 2026 edition of its annual GaN Insights, focusing on GaN gallium nitride (GaN) technology, its applications and future prospects, as the increasing adoption of GaN power solutions is driving a significant transformation in the power electronics industry...

What do e-bikes and laptops have in common? Both can be wirelessly charged by induction.

E-bikes and laptops both use lithium-ion batteries for power, chosen for their light weight, high energy density, and long lifespan. Both systems can be wirelessly recharged via the wireless power transfer (WPT) method that uses electromagnetic induction to transfer energy to the battery without cables.

For e-bikes, there is a wireless charging pad or inductive tile that e-bikes park on to transfer power. For induction charging, one coil is integrated into the static pad or tile (transmitter coil) and the other (the receiver coil) is situated on the bike, often in the kickstand. The charging pad’s coil, fed by AC, creates a magnetic field, which in turn produces current in the bike’s coil. This AC is then converted to DC, to power the bike’s battery.

The principle is the same for laptops, as well as a broad range of consumer and industrial devices, including small robots, drones, power tools, robotic vacuum cleaners, wireless routers, and lawnmowers.

Microchip provides a 300-W electromagnetic inductive wireless electric power transmission reference design that can be incorporated into any type of low-power consumer or industrial system for wireless charging (see block diagram in Figure 1). It consists of a Microchip WP300TX01 power transmitter (PTx) and Microchip WP300RX01 power receiver (PRx). The design operates with efficiency of over 90% at 300-W power and a Z-distance (the distance between pairing coils) of 5−10 mm.

Figure 1: Block diagram of the 300-W inductive power transfer reference design (Source: Microchip Technology Inc.)

The transmitter (Figure 2) is nominally powered from a 24-V rail and the receiver regulates the output voltage to nominal 24 V.

Figure 2: Block diagram of the power transmitter (Source: Microchip Technology Inc.)

The design’s operating DC input voltage range is 11 V to 37 V, with input overvoltage and undervoltage protection, as well as overcurrent and thermal protection via a PCB/coil temperature-monitoring functionality. Maximum receiver output current is 8.5 A, and the receiver output voltage is adjustable from 12 V to 36 V.

The design implements a Microchip proprietary protocol, developed after years of research and development and, with patents granted in the U.S., ensuring reliable power transfer with high efficiency. The system also implements foreign object detection (FOD), a safety measure that avoids hazardous situations should a metallic object find its way in the vicinity of the charging field. Once the FOD detects a metallic object near the charging zone, where the magnetic field is generated, it stops the power transfer.

The reference design incorporates this functionality on the main coil, ceasing power from the transmitter until the object is removed. FOD is performed by stopping four PWM drive signals, with four being the maximum to avoid stopping the charging entirely.

This reference design also detects some NFC/RFID cards and tags.

Transmitter and receiver

The WP300TX01 is a fixed-function device designed for wireless power transfer, as is the WP300RX01 chip, designed for receiving wireless power. The two are paired together for a maximum power transfer of 300 W.

The user can configure the input’s under- and overvoltage, as well as the input’s overcurrent and overpower. There are three outputs for general-purpose LEDs and multiple OLED screens, as well as five inputs for interface switches. The design enables OLED display pages to allow viewing and monitoring of live system parameters, and as with the input parameters, the OLED panel’s settings can be configured by the user.

The WP300RX01 device operates from 4.8 V to 5.2 V, in an ambient temperature between −40°C and 85°C. Like with the transmitter controller, this device provides overvoltage, undervoltage, overcurrent, overpower, and overtemperature protection, with added qualification of AEC-Q100 REVG Grade 3 (−40°C to 85°C), which refers to a device’s ability to function reliably within this ambient temperature range.

The reference design simplifies and accelerates WPT system design and eliminates the need to go through the certification process, as it has already been accredited with the CE certification, which signifies that a product meets all the necessary requirements of applicable EU directives and regulations.

Types of wireless charging

There are different types of wireless charging, including resonant, inductive, electric field coupling, and RF. Inductive charging for smartphones and other lower-power electronic devices is guided by the Qi open standard, introduced by the Wireless Power Consortium in 2010, to create a universal, interoperable charging concept for electronic devices.

The Qi open standard promotes interoperability, thus avoiding multiple chargers and cables, as well as market fragmentation into different proprietary solutions. Many manufacturers have adopted this standard in their products, including tech giants like Apple and Samsung.

Since 2023, the Qi 2.0 version brings faster charging to mobile devices to 15 W, certified for interoperability and safety. Qi 2.0 devices feature magnetic attachment technology, which aligns devices and chargers perfectly for improved energy efficiency for faster and safer charging and ease of use. Qi 2.X includes the Magnetic Power Profile (MPP) with an added operating frequency of 360 kHz. With MPP, a magnetic ring ensures the receiver’s coil aligns perfectly with the charger’s coil, thus improving power transfer and reducing heat.

Qi 2.2, released in June 2025, enables 25-W charging, building on the convenience and energy efficiency of Qi while improving the wireless charging time.

Simultaneous charging of two 15-W Qi receivers

In addition to its 300-W electromagnetic inductive wireless electric power transmission reference design reviewed earlier in this article, Microchip also offers the Qi2 dual-pad wireless power transmitter reference design. This dual-pad, multi-coil wireless power transmitter reference design enables simultaneous charging of two 15-W Qi receivers (see Figure 3).

At the heart of the design is a Microchip dsPIC33 digital-signal controller (DSC) that simultaneously controls both charging pads. The dual-pad design is compatible with the Qi 1.3 and Qi 2.x standards, as well as MPP and Extended Power Profile.

The hardware is reconfigurable and supports most transmitter topologies. In addition to MPP, it supports Baseline Power Profile for receivers to 5 W.

Figure 3: Block diagram of the Qi 2.0 dual-pad wireless power transmitter reference design (Source: Microchip Technology Inc.)

The MPP charging pad initiates charge with a 12-kHz inverter switching frequency but will shift to 360 kHz when connected to an MPP PRx. The dsPIC33CK DSC executes two charger instances. To facilitate support for different protocols, real-time decisions based on charging pad and receiver type are required.

The MPP charging pad initiates charge with a 12-kHz inverter switching frequency but will shift to 360 kHz when connected to an MPP PRx. The dsPIC33CK DSC executes two charger instances. To facilitate support for different protocols, real-time decisions based on charging pad and receiver type are required.

The software-based design provides a high level of flexibility to optimize key features of the wireless power system, such as efficiency, charging area, Z-distance, and FOD. To support applications with a wide input voltage range, each PTx includes a front-end four-switch buck-boost (4SWBB) converter for power regulation. The 4SWBB connects to a full-bridge inverter for driving the resonant tank. On the MPP charger, additional resonant capacitor switch networks enable higher resonant frequency. An MP-A13 charger implements a similar coil select circuitry for energizing the coil with the strongest signal possible, enabling a wider area of placement.

This reference design is automotive-grade and includes CryptoAuthentication, hardware-based (on-chip) secure storage for cryptographic keys, to protect communication and data handling. In addition, the design includes a Trust Anchor TA100/TA010 secure storage subsystem. The dsPIC33CK device architecture also allows the integration of additional software stacks, such as automotive CAN stack or NFC stacks for tag detection.

It’s worth noting that the variable-input voltage, fixed-frequency power control topology implemented in the transmitter is ideal for systems that must meet stringent electromagnetic-interference and electromagnetic-compatibility requirements.

In addition to all these features, including FOD through calibrated power loss, the dual-charging reference design also provides measured quality factor/resonant frequency and ping open-air object detection; multiple fast-charge implementations, including for Apple and Samsung; and several receiver modulation types, such as AC capacitive and AC/DC resistive. For added safety, the design includes thermal power foldback and shutdown and overpower protection.

A UART-USB communication interface enables reporting and debugging of data packets, and LEDs indicate system status and coil selection. There is a reset switch and temp sensor inputs for added functionalities.

With the continuously evolving standards for Qi and unique new applications requiring higher-wattage wireless charging, there is plenty of opportunity for innovation and growth in the wireless charging space. Microchip experts can provide you with the right guidance for seamlessly bringing your wireless charging solution to market.

 

 

 

 

 

 

 

 

 

 

 

 

 

 

 

The post Simplifying inductive wireless charging appeared first on EDN.

Звіт ректора за 2025 рік kpi вт, 02/10/2026 - 15:00